Solar Controlling and Charging
Here are my objectives with this charger.
Reject Dump current continually adjusted to keeps Solar Pannel voltages at optimum efficiency range of 17 to 18 volts.
Output regulation of .02vpp. The old design, being an chaotic regulator, had "mini-cycling".
It also was a pulse design with its inherent minicycling.
The new design will have solid regulation as smooth as silk,
where loading and charging can be tolerated at the same time.
Battery Bank voltages continually adjusted to battery temperature.
Initial design will be for only lead acid with its unique charging phases.
Equilization, (perhaps desulfinization), saturation, float, etc
Before I begin, I will create a starting point. Here is my basic regulator before I begin developing...
I create the circuit and try several different components. Here, in the picture, the toroidal chokes are about 50.3 uH.
I choose 1000 uF electrolytics on the input and output, as with my first Controller.
I do not like to have any electrolytics anywhere because they have a finite lifetime.
And if they get warm, it gets worse; they only live a couple of years.
But I have no choice in their use here at the initial input side, and also on the final output side.
Also, this stabilizes somewhat input and output to be always the same loading.
I am still using the same P-Channel MOSFET IRF4905.
Its resistance is not that bad: 0.02 ohms. And with my old design, even at 10 amps of current, the IRF4905 is only slightly warm.
And with any P-Channel, employed on the High Side, the Gate Drive is ridiculously simple.
After constructing the circuit, I immediatly I find all kind of problems:
The snubbers are red hot. I have to shut down and install resistors in series.
This is no permanent solution, but it will do while I investigate some of these other problems. There are many.
The chokes are too warm. And the only way to stop the heat is to install 1000uF electrolytics on the other side of the chokes.
Totally an unexceptable solution. Also the electrolytics are slightly warm. That too is totally unacceptable!
Also, if this is not bad enough, the IRF4905 MOSFETs have some Switching Heat.
I am only running two amps of current in this preliminary design.
Any heat at all in the regulator now, will be unacceptable later at 15 amps.
Regulation is not good at about .1 volt, at 12.6volts and 2 amps.
Nothing is working...
But first, I must address the TL594 PWM control problem.
In my first design using a PIC to control the MOSFET, I had no problems with regulation.
It was a variable frequency, and variable Pulse Width: It was what I call a simple Chaotic regulator, and it worked good.
Now I am using the TL594 PWM chip driving a power MOSFET IRF4905, actually four TL594s driving four IRF4905s
And before with the first design, a PIC performed the intrinsic manipulation of the MOSFET.
Now the PWM chip operates the MOSFET, and with such exclusive dedication, higher speeds are possible, as well as more smoother and consistent operation.
Two scope channels:
Monitoring Gate, showing drive pulses
Monitoring Slopes pin5 TL594
2.4cm is 0.24mS, and is 4.2kHz master oscillator freq.
I choose oscillators to run at aproximatly 4kHz.
The problem is that on pin one of the TL594 filtering is important.
Here, a 10k Ohm resistor and a 0.0147 uF cap form the input filter.
Because there is no capacitor on the TL594 PWM chip input, and because there is no feedback resistor, the
TL594 gain is set to maximum. When the gain is too high there are multiple decisions on the slop line.
Here, you can see, there are 10 decisions per slope line session.
This makes the system regulators and chokes, operate instead of 4kHz,
now run at 10 times the intended frequency; or 40kHz.
Multiple decisions are not desireable for another reason: poor regulation on the output.
Here the regulation is 0.05volts at 12.6 volts; Not good enough!
There is another reason too: The chokes and capacitors are going to be harder to tune at different frequencies.
The planned frequency must be set. I will arbitrarily set this to 4 kHz.
Here a 0.004 uF CAP is applied to the input of TL594 PWM Controller.
There are two decisions per slope line session.
Regulation is getting better.
Temperature of regulator heatsink tops out at 93 degrees in half hour with ambient at 84 degrees.
Adding a .01 cap yields exactly one decision per slope,
and synchronizes the decession at the top of the slope to always release.
This picture is out of sequence. I have added and changed several things,
the only pertinent thing is that the capacitor size is now 0.004 + 0.01 in parallel (0.0147uF).
We are done with the TL594 PWM. Now we can turn our attention to other matters.
Monitoring Output of Input Choke.
My invented band gap snubber clamps the input to 5.1 volts above average baseline (19volts),
and 5.1 volts below average baseline.
This is great, but the two zeners get way too hot.
I will increase gap to plus minus 9v.
I have removed the "conventional" snubber and let the input choke ring.
I have replaced the two 5.1 zeners with 9 volt zeners, giving an 18 volt swing band.
The zeners now run somewhat cooler.
The choke swings up to 33volts. The gate of the IRF4905 switcher pulls down to about 3 volts before releasing.
Here is the TL594 PWM oscillator sawtooth superimposed.
Scope setting is 50uS/cm.
Ring period is about 25uS, which is 40 kHz.
Input Choke is 69.5 uH.
Input Choke is 100nF cap plus 44nF internal
Input Choke is 0.03 ohms
Actually, the in circuit capacitance reads 160nF.
Now, I am going to make changes...
The inductors run warm; Maybe too warm.
But the snubbers run very hot. That is a deal breaker!
The zeners are too hot to touch. The diodes are quite warm.
Without the snubbers, the coils themselves get way too hot.
I plan to still use these iron inductors, but the input coil to the IRF4905 MOSFET switch,
and the first coil on the output side of the MOSFET switch MUST be air;
they take the brunt of the di/dt. Otherwise these chokes will get way too hot.
The torodials and straight chokes with ferrite material will not work. They get too hot.
Fascinating to put a screwdriver into an open air inductor. The air inductor is cool to the touch without the iron inside.
However, if you put a screwdriver shaft inside the choke,
and leave it there for a half minute,
and then pull it out, then you will find the shaft too hot to safely touch.
This is with the shaft out. This coil is 4.1uH, configured as an air coil.
There is little resistive components, and the waveshape fluctuates, producing a ragged look.
But the important thing is that the coil is cool. Yes, I can snub it all out producing a couple of nearly flat lines.
But why? Snubbers produce heat. And values are safe: only spiking to 35volts.
It is not pretty, being all jiggly, but it works.
Bottom trace is at gate of MOSFET IRF4905 switch. Top trace is at this choke as it goes to IRF4905 switch input.
The choke is running at about 21 volts, and takes a very fine quick initial spike low as the gate (bottom trace)
is driven low.
During the rest of the driven period,
it does not matter as long as the driven period remains low at about 5 volts, as it does.
The spike delays full conduction, and yields a cleaner switch,
producing less heat in the switching action of the MOSFET.
This is with the screwdriver inserted inside the coil.
Inductance increases dramatically.
Reactive component increases, but the resistive component dominates by killing changes by turning them into heat.
Changes do not linger.
Don't touch the blade of the screwdriver when you pull it out!
Here is an air coil, 36 wraps, #14. It will be one of the output coils. There are two per channel.
Four channels equal eight of these coils.
The Source Inductors are #12. They are planned to handle 15 amps.
Perhaps I should have made the output coils #12 too.
I'll take a little time out to see if the meter is correct...
Inductance is a convenient coefficient of Current (I) to obtain the total magnetic Flux.
And all it is, here in this coil, is a construction parameter. It is just Geometry.
So current multiplied by this construction geometry (L) yields the flux.
This is going to be somewhat a guess: I constructed a two layer coil.
And this math only applies to a single layer. But close enough is good.
A is the area of a single turn, a single loop, pi r squared.
Magnetic strength (B) inside coils is u times current times the ratio of Turns-per-meter.
This is also a construction. And it is a construction of a single layer.
But what is compensating in my favor is that I am assigning a single layer 36 turns,
and that is not true.
The first layer is only 18 turns. Hopefully it will be a wash.
It reads 4uH, and I calculate 5uH, but that is close enough.
This is the type of thing that only an empirical formula will work.
I don't know, but I would guess that a formally derived equation is beyond the quest of mere mortals.
Already I can see that the shape of my coils are not maximum. The denominator must have equal components.
The length must be about the same dimension as the diameter. The coil must be stubbier, not long and skinny.
But first I must get this thing to work with the inductance that I have: Each coil about 3uH.
I will work on optimization later when things at least work.
Back to work...
My invented "BandGap" snubber is still getting too hot! This will not work.
For this special RV application, there has to be a way to build a DC to DC controller that produces little or no heat.
My first controller produced practically no heat. But my objectives now are different.
Now, I want no pulses in the output.
I made a discovery: The waveshapes to the input and output of the regulator are mirror images!
Fortunately I started out with this project with a balanced system of chokes on the input and output.
That fortunate design has brought forth a revelation:
What would happen if the two sides were married with a capacitor?
What would happen if the RF Suppressor was replaced with a larger capacitor, and its function generalized?
I started out by increasing the regulators bypass cap from .1 uF to .47uF.
The condition grew worse. Did not seem like the thing to do...
I continued increasing the size; .47uF to 1uF to 10uF. The 10uF grew hot in my fingers.
And it was an electrolytic, to boot. But there was an improvement!
I them went to 47uF in a large hv electrolytic. Beautiful results!
The cap was slightly warm, but the results solved so many problems.
I did not even need the snubbers anymore. I really stumbled unto something!
(The BodyDiode in the MOSFET seems to not work very well under a one volt Vds difference)
The bottom trace is of the drive Gate of the IRF4905 switch.
The MOSFET pull up resistor shows a smooth hump of the input Source.
The input power rises in a smooth hump after the power demand is removed.
The upper trace is of the Source input of the MOSFET, and was illuded to by the Gate trace below.
(The upper trace is DC shifted up out of the way on the display so that you can see it.)
You can see as the Gate drive is driven low, the Source input falls.
So here on the bottom trace is the Output. And the number of 10uF, soon to be ceramic, capacitors is two.
You can see it is the mirror image of the other side of the IRF4905 MOSFET. Drain and Source are mirror images.
That is why this technique works so well.
However, I still had a slight problem; Not a problem for anyone else. But for an RV controller it was a problem.
The iron chokes still were warm. That is not acceptable for me and my application.
So now, I am going to all air chokes, and also I am ordering some 10uF caps in Ceramic.
All Air-Coils, and no more snubbers.
I have to start all over to tune this thing in...
Here is heavier current.
Bottom trace is of the gate.
Top trace is of the Drain output of the MOSFET switch.
You can see sustained "flat-line" output as the demand starves the source.
I have padded the source resistance, so that it can not deliver more that 12.8 volts with this load of 2.7amps.
This forces about a 50% duty cycle. When the output is not supplied, it decays into a smooth dip.
In comparing the input watts to the output watts:
In this case of 2.70Amps
41.6 watts input
34.0 watts output
Efficiency is 82%
The missing 7.6 watts is probably in the coils, as they are all warm to the touch and read about 98F degrees on the IR meter.
They are about 5 feet of wire each; 10 ft of #14, and 15 ft of #12.
That is 1.6/1000x15ft + 2.5/1000x10ft = 0.049 ohms, (2.70A)^2 * 0.049ohms = 0.35Watts
Well, obviously that does not account for the 7.6 watts. So it is not wire DC Resistance.
It must be AC Reactance in the coils. But I have never known that to happen.
I thought it impossible in Air-Core coils. That is a mystery!
Actually it is good news that the heat is not coming from DC current, because every thing would burn up at 15 amps.
There are no eddy currents in the iron core, because there are no cores of any kind.
But what about in the copper wire? Changing magnetic fields can induce current in anything.
I will return to this problem later.
I built the inclosure prematurely. The box is too small. Nothing fits.
I am using an old fashioned analog amp meter. It shows 2.7 amps. The one amp meter shows the total current to all four loads.
The loads are two battery banks, one utilities, and one reject load. Three dedicated meters are shown in blue; They two battery banks and one remote Utilities.
Another efficiency measurement:
Quiescent (night time) current: 30.6mA (5 meters, cpu board)
Input 2.69A, 15.38V 41.37W
Output 2.66A, 13.51V, 35.51W, Efficiency 85.8%
Diode 2.66A, 12.58V, 33.46W, Efficiency 80.8% GenPurp Diode 2.05w Measures: 0.765v x 2.66A=2.03W
Onboard Pannel Meter readings: 2.65A, 12.55V 33.3W
Regulation (OnB:12.60v,12.54v RemoteGround) (My:12.47v,12.47v SourceGround)
Removed community 5v Reference. Established individual 5 volt References from each TL594 PWM chip.
Diode: Replaced with Schottky. 0.33v cold, 0.32v hot 115F degrees at 2.6A.
Removed the third coil on input. There are now only two Chokes of #12 wire air coils of 3.52uH, 3.79uH.
Input Electrolytic gets warmer without that coil. But I am going to leave it out. Input regulation is not that important.
Just so the PIC can get an accurate measure of the input voltage from the solar panels under load. And it is solid.
However, the electrolytic will not last very long at 102F degrees, but I will worry about it later.
Building this thing may take awhile; I make a gain in one place and loose in another.
Output Regulation is OK from a no load of 13.00volts, to a 2.6A load of 12.99volts. Difference 0.01v at 2.6A
PWM starts at the upper part of the slope, and deepens with more demand to the left.
Actually, a more logical way to look at it is that the slope begins at the bottom, rises (tests the water) until the output matches slope voltage.
The conduction period is triggered. The earlier the trigger, the lower was the output voltage.
Here is a huge load and a huge amount of current to maintain the same voltage.
On the scope you can see the source voltage drops, less ripple in the input, and the conduction time increases.
The PWM timing remains the same. (I had my fingers on the scopes sweep speed.)
Took the box out to the RV. Ran about 5 amps for 2 hours. MOSFET temperature rose to 118F degrees.
That is way too hot. For comparison, my old MOSFET design does not even get warm to the touch at any amps.
With my old design, I can just barely tell that the heat sink is luke warm.
Top trace is the MOSFET Source voltage. Bottom trace is the MOSFET Gate voltage.
They kinda merge together at the top.
In contrast, this MOSFET gets burning hot!
Too much heat is being produced in the MOSFET.
So back on the scope you can see where the heat is coming from.
I have colored the heat producing areas in purple.
Of course, here is where the gate is just below the Source.
OK, now I am going to try another design, I will design a Gate Driver.
I will use two Emitter-Followers in a TotemPoll.
The NPN will dramatically decrease the pull up impedance.
Now both the pull down and the pull up will be driven.
The problem is that with any BiPolar transistors there is a .6 volt voltage drop across the junction.
So I have included a 1k resistor, in parallel with the voltage drop, from collector to emitter.
That should alleviate a lot of the 0.6 drop.
Wow! that really improved the up stroke. Sides are straight.
However, there still remains a little heat in the 0.6volt region just under and between the Source and the Gate during
the initial part of the hump. The 1k ohm resistor closes the gap but it is too slow initially.
Input: 14.76v, 2.71A, 40w
Output: 13.36v, 2.68A, 35.8W
Trial and error has led to this schematic...
Optimum use of the interval.
I am going to use the SourceDrain Cap to determine the MOSFET duty cycle,
and it is quite different and independent from the PW of the TL594 PWM Chip.
The other cap in the schematic, MOSFET output cap, only helps with regulation.
It also determines the ring frequency, but has no effect on conduction time.
The scope shows two displays with the SourceDrain cap totally disconnected.
The supply voltage is about 18VDC, and after ringing, settles to this value.
There is little capacity between Source and Drain and the Source voltage rings to about 40 volts.
I have moved the Source monitoring up and off the scope.
Of course this will not work, ringing is down into the conduction area,
and voltage rings dangerously high and too close to the 60 volt max for the HEXFET.
Also the Body Diode may be activated and produce even more heat.
Here is what is important:
With a display of 20uS/cm, there is about 12uS of conduction time.
As you add more and more capacity, the ringing diminishes and nearly stops at about 1uF.
This is one 10uF cap between Source and Drain.
Ringing has stopped except in the conduction zone.
Conduction time has decreased to about 6uS.
This will work: We must have some time on the conduction floor.
Heat is 94F degrees in half hour.
It is stable. 12 degrees above ambient.
Same conditions: .6 Amps, 13.00v output,
Here is with too much capacity between Source and Drain. It is 30uF.
Here is the same .6 Amps, 13.00v output, and as you can see, the switching time is extremely short.
There is no conduction time on the floor at all. And the temperature rises dramatically: about 107F degrees in a half hour.
In fact the .6 amps is a little more too: about 30mA more.
So this is clearly inefficient, and more heat is produced.
The total conduction time available is 106uS, as previously determined and set by the TL594 PWM Chip.
On the scope you can see about 5.5 cm of sweep.
But at the HEXFET, 0.6Amps takes up 6uS. Max possible is therefor 17.6Amps.
My goal is 15 amps so this is perfect! This is it: One 10uF Ceramic cap between Source and Drain.
The displays may seem counter intuitive; with the extremely short duration producing the same current as the 6uS trace.
The secret is that the short duration returns to near 100% baseline.
A powerful kick using capacitance between Source and Drain, is used to fill in.
The longer duration pulse suffers from the Source voltage
dropping at the same time as the pulse is trying to garner enough coulombs.
The source drops 7 volts instantly, and slowly recovers in a ring.
The duration has to increase to compensate for the lower Source voltage during the interval.
This is exactly what I want, more efficient use of the conduction pulse.
Otherwise, I may as well be operating at 100mHz and have huge switching losses.
No thank you: I will choose more practical on-floor time. Of course, my quiescent no load is 20mA.
And a short spike is OK here because the current is only 20mA. I can be wasteful here: the percentage is nothing.
There is another problem: When the four Regulator Outputs are applied to their loads.
It is the problem with the Schottkies.
Currents from the two Battery Banks, and the Utilities can not be allowed back into the MOSFETS.
Three of these Regulators most have a Schottky, as their loads contain voltage at night.
I do not see anyway around it. And they get quite hot with anything over 5 amps.
19.09V, 0.52A, 9.93W
19.12V, 0.52A, 9.94W
13.21V, 0.51A, 6.74W, 67.8%
12.90V, 0.51A, 6.58W, 66.2% with Diode, 0.16W 0.31V Schottky
15.40V, 2.53A, 39.1W
13.38V, 2.53A, 33.85W, 86.6%
13.03V, 2.51A, 32.71W, 83.6% with Diode, 1.1W 0.35V Schottky
Still; the schottky only represent a few percent of total heat losses.
And only 10mA of reverse current at night.
The 1k Source-Gate resistor is not eliminating the .6 volt gap.
If it is not working, why have it?
In the series of pictures below, this gap can clearly be seen.
But according to the specs for the MOSFET,
the gate needs to get below a couple of volts under the Source before conduction really begins,
so 0.6 is OK. Well... Maybe not. The Source will "track" the Gate; If the Gate goes low, the Source pulls low.
This would produce two parallel curves. And damn! That is what it looks like.
Removed the 1k Source-Gate resistor.
Here is the box, split into two: a top and a bottom.
I can use these speaker rheostats to soften the input.
I am using the automotive bulbs for loads.
Each bulb can use about 3 amps using both filaments.
This test setup is essential.
By introducing resistance into the input 19v, I can force a longer duty cycle.
I also have a way to measure efficiency directly:
By using a voltmeter across these rheostats, I can measure current.
Of course I can place a current meter directly in the 19v source input,
but I will not have three place accuracy.
Neither the output voltage nor the output current change.
So I can watch this voltmeter, wich is input current, change up and down
and see efficiency going up and down directly.
I just can not make any changes to the rheostats while I am looking at efficiency.
Taking the above Rheostats and increasing the resistance in the 19 volt supply,
results in an increasing duty cycle for conduction.
During the series of rheostats adjustments,
a change in the output current or voltage is not measurable at all.
Output voltage is a constant 13.00 volts.
The top trace is the HEXFET Source, bottom is HEXFET Gate.
I can not use heavy loads while these rheostats are connected; They will burn up.
In this run, I am only connected to the low filament of one bulb: That is only 0.6 amp.
This is as low as I can go. But the same results should be applicable to heavy loads.
You can see a gap between the Source and the Gate, and it seems to increase with a longer duty cycle.
But originally I chose the P-Channel because when used on the High Side like this,
I did not have to build a separate Gate Driver.
Perhaps it is not true:
Perhaps it does not matter when on the High Side,
N-Channel or P-Channel;
you must use some kind of exalted Gate Driver.
One that has higher voltages than what is natively available.
OK, I think I have got it. I built this Gate Driver. It is a Peak-Hold.
I could have used a germanium .3v diode but a silicon 0.6v does the job great.
Just for the porposes of the display,
I have DC level shifted the "flat line" of the Peak-Hold, which is the new power source of the TotemPoll.
Now the Gate will be slightly over driven in the positive direction.
Now, clearly, there is no doubt about a good cut off in conduction.
There seems to be no change in heat production, as I suspected,
but I will keep the circuit because "it looks better".
I wish I had a scope with different colors for the traces.
The top trace is the HEXFET Source, the bottom is the HEXFET Gate.
And as you can see, if the Source has a lot of activity on it, as in the first picture,
the Gate is way above the Source. This is great! In all other cases, at least they are equal.
This is a multistage charger.
I do things a little differently.
It is out of necessity. The RV is designed to operate in the fog, and low light.
Therefore, the equalization stage must be the first stage.
As soon as light is detected in the morning, the Charger goes into Equalization.
And it is maximum light energy conversion to battery energy, no matter what.
Light may not be available in the afternoon. All solar panel energy is shoved into the two battery banks.
The batteries come up to full charge at 14.4volts.
Gas production begins. But equalization pushes above this.
I push to 15.0 volts at 70 degrees at the batteries. The temperature is monitored.
I have never experienced it, but LeadAcid batteries at this voltage can go into thermal runaway.
This can result in warped cases, loss of water, and at the extreme: an explosion.
But I have had no heating and little loss of water. Necessarily, there must be some gassing to equalise all the cells.
Gassing on a high cell is necessary to get charging current to a low cell.
My system works because the resulting 15.0 battery volts is only allowed for one minute.
But it is applied every morning, every day, eventually equalizing all the cells of both banks.
Eventually, all cells will gas a tiny tiny amount at the same time, and the same amount.
Over a month, all cells are down the same 1/16 of an inch.
As soon as a battery reaches 15.0 volts, stage two is implemented.
By experimenting, I have found that anything from 14.7 to 15.2 will work.
This value is adjusted in code. For example, if batteries have light duty, and are not heavely discharged, then 14.7 works good.
For stage two, the voltage is dropped to normal operating voltage for the selected buss battery,
and a float voltage is applied to the standby bank. These voltages are manually adjusted by the three pots on the front of the Controller.
With the old design, equalizing could only be done on the standby battery bank.
And, to make matters worse, it used pulses of 20 volts which, if misapplied, could damage electronics in the RV.
This design works much better, and I do not have to keep track of which bank is being utilized.
Everything is done automatically. My charger can push 15Amps for hours untill stage one is met.
And one more addition...
Soldered this up on a small PC board, tested it, and took it out to the RV.
I was already familiar with the TL494, so it was a breeze to setup.
The same goes for the IRF4905 FET. This thing goes as close to the RV Utility fuses as possible.
It takes any voltage from the battery bank area,
and regulates it to 12.02 volts for all low voltage Utility fuses.
Works in the RV at high currents too. I am using 12 amps for my soldering gun all the time.
And my drill pulls about 15 amps. Both of these come from the 120 volt inverter.
I am fascinated how one FET in this tiny regulator does not get warm.
I hammered it with 12 amps from my soldering gun for 30 secs, and there was no detectable warmth.
But the day will come when I will need more current,
and for perhaps no more of a reason than esthetics, will have to make it at least look larger.
Here is the PostReg inside the Fuse Box. The red light is coming from the LED that drives the gate.
It flickers, changing intensity according to the load. I like to be able to "see" the regulation.
And to see it, I do not mind cutting out a couple of vents.
I do not know what to call this thing. I invented its function.
I am probably the only person with an RV that has it.
It is a "final" regulator. And in a grander scheme with more stuff in it,
I could name it a "Utility Conditioner". I predict, someday, high end motorhomes will have my invention.
There are reasons why I need this thing:
This is needed to insure the RV refrigerator, Inverter and other electronics are not driven too high with 16 volts.
Now, that Active Equalization is performed every day on the batteries, the voltage inside the RV can rise to dangerous levels.
I have never had a problem, but why push it.
Also, the RV Furnace which pulls 7.5 amps runs more efficiently.
I would rather run the Furnace at 12.0 volts than 12.5 volts.
The air flow is less but the batteries last longer.
Also, there are many analog 5 volt regulators throughout the RV.
All of the 5 volt regulators, which are not switching type regulators,
will run cooler and more efficiently.
They are now fed with 12.02 volts instead of 13.5 or 14 volts.
They run more safely and cooler.
Over the past three years, I have noticed some of my homemade LED Clusters have been growing dim.
They do not use current drivers, and I think I have been over driving them.
The LEDs have been exposed to a raw 12 volts that is all over the place,
and can have a sustained high voltage for hours.
A steady and safe 12.02 Volts should stop the degradation.
Also, with this device, I can mix my Lead Acid batteries with Lithium Ion batteries.
As far as I know, no one has done that before me.
With this device, Input voltage levels, or input batteries, do not matter.
I can keep my two Lead Acids, and also have two Lithium Ions, and have all feeding the Utilities at the same time.
The new voltage at the RV Utilities is 12.02 volts.
And the middle unboard regulator no longer controls it; The PostRegulator does.
For now the middle switch is simply turned off.
One might think that there is an engineering loss in effort, at least waisted time.
After all, I designed a Utilities Regulator,
fed directly with its own dedicated remote sense, that is now gone; just waisted time.
Not so! Things develope and change, and as an engineer, I do not mind.
In fact, for an engineer, change is a welcome opportunity.
Actually, it may not be waisted effort on that middle switch.
By leaving the switch on, modifying the adjustment range,
and adjusting to 12.00 or 11.95 volts at the Utilities (just under the 12.02v),
something neat happens:
Nothing happens, if and until the Post Regulator drops to under 12.02 volts.
Then there is yet another source for current into the Utilities.
I have literally added another wire, or effectively decreased the wiring resistance from the Batteries.
Here is the Solar Collection Panel...
I have not properly labeled the switches yet.
Switch 1: 100 Watt Panel
Switch 2: 80 Watt Panel
Switch 3: Combined 50, 30, 10 Watt Panels
Switch 4: 100 Watt Panel
Switch 5: 100 Watt Panel
The enunciator knob adjusts the volume of the vocalizations from all autonomous RV devices.
All my devices that I have ever invented can talk.
I also monitor Solar Sounds from the sun.
The Solar Sounds are pre-set in volume, but come through the same amp and speaker as speech.
The Solar Flux is 27% percent. This sensor is one of two mounted atop the Air Conditioner.
The RV Utility voltage is 12.00 volts. It seems to vary slightly.
It is usually 12.02 or 12.01 depending on inside RV temperature.
Here Battery-one is in equalize mode and is pulling almost 9 amps. There are two solar flux sensors.
Both are mounted on the Air Conditioner. The Controller has its own dedicated sensor and it reads 42%.
Characteristically for this location at Black Butte, with some oak limbs overhead, you can devide the solar input percent by, an arbitrarily and roughly, "three" to get the max amps.
In this case 42/3=14 amps max possible.
Early this morning with pure sky light and little shadings, 1.0% solar input, which is where things begin to work, was producing roughly 300mA.
Of course, if I wanted it more exact, I could look at, and test, each panel individually exactly with the switches at the Collection Panel.
A general collection from the intire roof is more convenient, because no dought some panels may be shaded.
The RV can be in full sun, and yet a pedicular panel can be shaded by a leaf, or shaded by the Air Conditioner, or the antenna if it is up.
And inherent shading from objects on the roof is worse at low sun angles of the morning and evening.